實驗室 flyback converters -...
TRANSCRIPT
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808 ()
Ying-Yu TzouFlyback ConvertersYing-Yu TzouYing-Yu Tzou Ying-Yu Tzou Ying-Yu Tzou2008215 -
Flyback Converters
, Sept. 2006. 808-PowerLab 1
1/57
Flyback Converters
Power Electronics Systems & Chips Lab.
Power Electronics Systems & Chips Lab., NCTU, Taiwan
2/57
Flyback Converters
Derivation of the Flyback ConverterFeatures of Flyback ConverterWhy Choose the Flyback Converter?Properties of Flyback ConvertersDisadvantages of the Flyback ConvertersOperating Principle of the Flyback ConverterTypical Waveforms of the Flyback ConverterDesign EquationsFlyback Converter Transformer-ChokeCross Regulation in Multiple Outputs Flyback Converters
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Flyback Converters
, Sept. 2006. 808-PowerLab 2
3/57
Invention of the Flyback Converter
How to design an isolated buck-boost converter with minimum number of components?
vo
vg
?
4/57
Derivation of the Flyback Converter
(a)
Vi Vo
+
L+
(b)
Vi Vo
+
L1+
L2
(c)
Vi Vo
+
L2L1
(d)
Vo
_
+
L2Vi
L1
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Flyback Converters
, Sept. 2006. 808-PowerLab 3
5/57
Features of Flyback Converter
The isolated flyback converter is basically a buck-boost derived converter with an isolation winding, so that the input circuit is isolated from the output circuit, and the output voltage can be either positive or negative, depending on the winding and diode connected polarities.Application: Lowest cost, multiple output supplies in the 5-150W range. E.g. mains input T.V. supplies, small computer supplies.
DC-DC ConverterInput Stage
AC LineInput
Vout
+
+
PWMVSENSE
Isolati on
6/57
Why Choose the Flyback Converter?
Flyback power supplies use the least number of components. At power levels below 75 watts, total flyback component cost is lower when compared to other techniques. Between 75 and 100 Watts, increasing voltage and current stresses cause flyback component cost to increase significantly. At power levels higher than 100 Watts, topologies with lower voltage and current stress levels (such as the forward converter) may bemore cost effective even with higher component counts.
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Flyback Converters
, Sept. 2006. 808-PowerLab 4
7/57
Properties of Flyback Converters
In design of a flyback power supplies, transformer design is usually the biggest stumbling block. Flyback transformers are not designed or used like normal transformers. Energy must be stored in the core, the core must be gapped, and the transferred energy is stored in the air gap. The air gap inductance represents most of the magnetization inductance. However, this magnetization inductance is relative small.
n : 1 +
+
oI
VoVin
Co RD
Q
8/57
The Flyback Transformer
n : 1 +
+
oI
VoVin
Co RD
Q
n : 1 +
+
oI
VoVin
Co RD
Q
LM
Transformer Model
The air gap inductance represents most of the magnetization inductance.
LM
Ideal Transformer
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Flyback Converters
, Sept. 2006. 808-PowerLab 5
9/57
The Flyback Transformer
A two-winding inductor Symbol is same as transformer, but function differs significantly from ideal transformerEnergy is stored in magnetizing inductanceMagnetizing inductance is relatively small
Current does not simultaneously flow in primary and secondary windingsInstantaneous winding voltages follow turns ratioInstantaneous (and rms) winding currents do not follow turns ratioModel as (small) magnetizing inductance in parallel with ideal transformer
n : 1 +
+
oI
VoVinCo RD
Q
LM
Transformer Model
10/57
Current Flow in Flyback Converter
Current effectively flows in either the primary or secondary winding but never in both windings at the same time.
n : 1 +
+
oI
VoVin
Co RLM
Q ON and D OFF
I outT
T
inV2
inV
on off onvgs
VDS
Ip
Is
Io
Q OFF and D ONn : 1
+
+
oI
VoVin
Co RD
LM
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Flyback Converters
, Sept. 2006. 808-PowerLab 6
11/57
Current Flow in Flyback Converter
Q OFF and D OFFn : 1
+
+
oI
VoVin
Co RD
LM
I outDT
T
inV2
inV
on off onvgs
VDS
Ip
Is
Io
12/57
Flyback Converter in Discontinuous Conduction Mode
I outDT
T
inV2
inV
on off onvgs
VDS
Ip
Is
n : 1
+
+
IoVin
Co R
Ip
Q
D
vgs
Vo
Io
Is
p
satCEDC
LVV
dtdI )(=
The Primary Current rising slope:
Peak Primary Current:p
satCEDCp L
DTVVI
)( )(=
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Flyback Converters
, Sept. 2006. 808-PowerLab 7
13/57
Flyback Converter in DCM
A1
A2
A1 = A2
(a)
(b)
(c)
(d)
Ip
IsTon
Tr Tdtdcpmdc )V/N(NV +
dcV
C1
Vdc
D1T1
Nsl
Vat
D2
Nsm
Vom
C0 R0
R1
R2
EAVref
DC voltage-controlledv ariable width
pulse generator
Q1
Lp
Np
s
pps N
NII =
14/57
When the Primary Switch Is ON
+
+
VoVin
Co R
Q
Ip
Ton
Ip
Lp Primary Magnetizing Inductance
L1 Lg L2
g
2g1p
L//L//LLL
=Lp
21g //LLL >>Q
Io
The secondary diode is reverse biasedThe load power is supplied by the output capacitor The primary current store energy into the primary magnetizing inductance!
Lg
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Flyback Converters
, Sept. 2006. 808-PowerLab 8
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Energy Stored in The Magnetization Inductance
+
+
VoVin
Co R
Q
Ip
Ton
Ip
Lp Primary Magnetizing Inductance
Io
2)(IL
E2
pp=The Maximum Stored Energy is:
Most energy is stored in the air gap!
CoLg
The Gap Effect
16/57
Release The Stored Energy to the Output Rectifier
+
+
VoVin
Co R
D
Q
Lg
Ip
Ip Is
Lp Primary Magnetizing Inductance
Io
s
pps NN
II =
Ip(max) 2)(ILE
2ss=
The released energy is equal to the stored energy when operating in steady state.
When the Primary Switch Is OFF
Ton
Toff
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Flyback Converters
, Sept. 2006. 808-PowerLab 9
17/57
Flyback Converter: Typical Waveforms
nuu 1
2
10
=
s
u eb
u 1
i
n : 1
C RL
ioD
+
-
+
-u ce
21 u O
I
T
T
S
u ce
n
1
T2
Ni
T
T
u1
s
s
s s
s
2
1
S
u ce
n
1
i
ii
2
Ni
DCM CCM
i
18/57
Typical Characteristics n : 1 +
+
IL
VoVin
Co R
Suitable for Off-line SPS under 75 Watts
Typical converter efficiency: = 80%
Max. duty ratio: Dmax = 45%
Max. transistor voltage: Vds = 2Vin(max) + leakage spike
DC voltage gain (CCM):
DC voltage gain (DCM):
D-1Dn
VV
in
o =
P
L
in
o
LT
2RnD
VV
=
Note: DCM buck-boost characteristic is linear.
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Flyback Converters
, Sept. 2006. 808-PowerLab 10
19/57
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Flyback Converters
, Sept. 2006. 808-PowerLab 11
21/57
Buck-Boost Converter: CCM and DCM Static Characteristics
CCM DCM
K1
Buck-
boos
t
0 0.2 0.4 0.6 0.8 1.0
1.0
D
CCMM(D, K)
Buck
Boost
0 0.2 0.4 0.6 0.8 1.0
1.0
D
CCMM(D, K)
22/57
Output Power and Voltage as a Function of PWM Duty
+
+
VoVin
Co R
Q
Ip
Ton
Ip Io
2)(IL
E2
pp=The Maximum Stored Energy is:
CoLg
The Average Power Pass Through The Choke-Transformer
[Watts] 2T
)(ILP
2pp
avg =
p
ONsatinp L
)TV(VI =Q [Watts] 2TL)T(V
2TL)])TV-[(VP
p
2ONin
p
2ONsatin
avg ==
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Flyback Converters
, Sept. 2006. 808-PowerLab 12
23/57
Voltage Conversion Ratio in DCM Operation
+
+
VoVin
Co R
Q
Ip Io
CoLg
Pi Input Power Po Output Power
+
=Tt
t pini0
0(t)dt(t)iv
T1P=Power Input Average
+
=Tt
t o
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Flyback Converters
, Sept. 2006. 808-PowerLab 13
25/57
Turn Ratio Maximum Switch Voltage
n : 1 +
+
oI
VoVinCo RD
Q
LM
Transformer Model
Maximum OFF-Voltage Stress?
age)spike(leakdiode(on)os
pdc(max)Q(max) V)V(VN
NVV +++=
Max. transistor voltage: Vds = 2Vin(max) + leakage spike
Worst Case Condition:
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Ensure Core Does Not Saturate Remains in DCM Mode
Ip
Is
+
+
VoVin
Co R
D
Q
Lg
Ip IoIp(max)
Ton
ToffTo guarantee the core does not saturate, the stored energy must be completely released!
TR
Reset Time
A
B
A = B
Rs
pdiode(on)oon(max)Q(on)in(min) TN
N)V(VTV(V += )
Tdt
Dead Time
A 20%T dead time margin will limit the maximum output voltage with a specified turn ratio!
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Flyback Converters
, Sept. 2006. 808-PowerLab 14
27/57
Why Flyback Converters Are Usually Designed in DCM Mode?
To Ensure Core Does Not Saturate
Saturated! Not Saturated!
Ip
DIV21
T
TI21
V P pinONp
ini ==
To get larger input power , we need higher input current! To ensure the inductor does not saturate, we need to reduce the inductance! This also implies a lower volt-second product. For a same DC input, it means a lower duty ratio!
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Why Flyback Converters Are Usually Designed in DCM Mode?
To Avoid Sub-Harmonic Oscillations Due to Duty Divergence
For peak current mode control, when the current falling slope is greater than the rising slope, i.e. |m2|>|m1|, this occurs when the converter reach into the CCM region, the current will diverge under a constant current reference. To avoid this phenomena, we can restrict the converter operating in DCM mode. If the converter needs to be operated in CCM mode, then a negative slope compensation is needed to stabilize this sub-harmonic oscillations.
I. Zafrany and S. Ben-Yaakov, A chaos model of subharmonic oscillations in current mode PWM boost converters, IEEE PESC Conf. Rec., pp. 1111-1117, 1995.
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Flyback Converters
, Sept. 2006. 808-PowerLab 15
29/57
Determination of Turn Ratio
Np : Ns+
+
oI
VoVinCo RD
Q
LM
Transformer Model How to determine turn ratio?
Rs
pdiode(on)oon(max)Q(on)in(min) TN
N)V(VTV(V += )
TTTT dtRon(max) =++
If a 20% dead time is specified as the safe margin, then 0.8TTT Ron(max) =+
)/N)(NV(V)V(V)0.8T/N)(NV(V
Tspdiode(on)oQ(on)in(min)
spdiode(on)oon(max) ++
+=
30/57
Determination of Turn Ratio ..
s
p
NN
n =Define
)/N)(NV(V)V(V)0.8T/N)(NV(V
Tspdiode(on)oQ(on)in(min)
spdiode(on)oon(max) ++
+=
nVVn0.8TVT
21
2on(max) +
=
diode(on)o2 VVV +=Q(on)in(min)1 VVV =
TTT Ron(max) +=Define
max
max
diode(on)o
Q(on)in(min)
D-D
VVVV
n+
=
The proper turn ratio must be determine to ensure the DCM operation under a minimum input voltage, maximum specified duty, and a safety dead time ratio.
For the DCM flyback transformer design
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Flyback Converters
, Sept. 2006. 808-PowerLab 16
31/57
Determination of Primary Inductance
Lp Primary Magnetizing Inductance
Np : Ns+
+
oI
VoVinCo RD
Q
LM
Transformer Model
To ensure the flyback converter operating in DCM mode:
IpIp(max)
Ton
T
TR
Reset Time
Tdt
2
=
o
on(max)in(min)op V
TV2TR L
T
)I(L21
RV
1P
1 P
2pp
o
2o
oi ===
32/57
Design Equations: Maximum Switch Current (DCM)
Max. transistor current:
n : 1 +
+
IL
VoVin
Co R
p
on(max)dc(min)p(max) L
TVI =
Ip(max)
Ton(max)
maxE
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Flyback Converters
, Sept. 2006. 808-PowerLab 17
33/57
Primary RMS Current and Wire Size
Ton(max)
p
on(max)dc(min)p(max) L
TVI =
TT
3I
I on(max)p(max)p(rms) =
T
At 500 circular mils per rms ampere, the required number of circular mils is:
TT
3I
500I (primarty) required mils Circular
on(max)p(max)
p(rms)
=
=
34/57
Definition of Circular mils
mils = thousandths-of-an-inch
1 circular mil = define the Area of a circular wire with a diameter of 1 mil1 square mil = define the Area of a square wire with width of a mil
Current Notes:The current shown per wire size listed above is based on 1 amp/700 Circular mils, other tables provide different current per wire size, and different current for open air ~ check your local electrical code for the correct current capacity [Ampacity]. The 1 amp/ 700 Circular mils seems to be the most conservative, other sites provide/allow for 1 amp per 200 or 300 Circular mil. For shot wire lengths use 1A/200 Circular mil, for longer wire runs use 300 Circular mil, and for very long wire runs use the table above, 1 amp / 700 Circular mil.
817.7.57726.1740420.124
648.4.72820.7651122.623
514.12.91816.4664025.322
407.81.1613.0581228.521
323.41.4610.35102432.020
256.51.848.210128935.919
203.42.326.510162440.318
161.32.935.163205245.317
127.93.694.094258150.816
101.44.653.247326057.115
80.445.872.575410964.114
63.807.402.042518472.013
50.599.331.619652980.812
Feet per Pound
Current Carrying
Ohms/1000ft
Circular mils
Diam. (mils)AWG
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Flyback Converters
, Sept. 2006. 808-PowerLab 18
35/57
RMS Values of Typical Waveforms
A period sinusoidal waveform with amplitude of A, its half period average value is 2A/ (0.636A) and RMS value is .2/A
A
AA
F RMS 707.02(sin) ==
AsqrF RMS =)(
AAtriF RMS 577.03)( ==
AF AVG 2(sin) =
AsqrF AVG =)(
2)( AtriF AVG =
Triangular wave
SIN wave
Square wave
1.151.732
1.111.414
11
Form FactorCrest Factor
36/57
RMS Values of Typical Waveforms ..
2
311
+=
IIII RMS
pkRMS II =
II RMS =i(t)I
t
pkI
pkI
i(t)
t
i(t)
t
II
Ts
Ts
3II RMS
=
321 DDII pkRMS
+=
3D
II pkRMS =
i(t)
0t
I
i(t)
0 t
i(t)
t00
0
Ts
Ts
DTs
D1Ts D2Ts
pkI
pkI
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Flyback Converters
, Sept. 2006. 808-PowerLab 19
37/57
Primary RMS Current and Wire Size
Ip
Ton
T
TR
Reset Time
Tdt
p
on(max)dc(min)p(max) L
TVI =
s
pp(max)s(max) N
NII =
TT
3)/N(NI
I rspp(max)s(rms) =
At 500 circular mils per rms ampere, the required number of circular mils is:
s(rms)500I )(secondary required mils Circular =
38/57
Flyback Transformer
The ideal flyback transformer operating as an ideal transformer parallel with a magnetization inductance. This magnetization inductance is the value required for a buck-boost converter. Therefore, the flyback transformer performs the function of an inductor as well as a transformer. To let the flyback transformer carry large primary current without saturating, the core is selected as
Gapped Ferrite CoreMPP (Molybdenum Permalloy Powder) Core
In practical realization of the flyback transformer, it is difficult to keep the leakage inductance small, especially when the rated power is increased.
Is
+
+
VoVin
Co R
D
Q
Lg
Ip Io
-
Flyback Converters
, Sept. 2006. 808-PowerLab 20
39/57
Energy Stored in an Inductor
Mean path length l Cross-sectional area A
Permeability
I
N: number of turns
lANL 2=
The energy stored in the core:
===tt
L LIdiLiPdtE 02
0 21''
The energy density (energy/volume) is:
2
211
2
22
222221
B
NlB
lAN
AlAlLI
B
=
==
The energy stored in the core:
coreBL VLIE ==2
21
Vcore: volume of the core
2
2r0
2
2c
core BLI
BLIV ==
40/57
Flyback Converter Transformer-Choke
Since the transformer-choke of the flyback converter is driven in one direction of the B-H characteristic curve, it has to be designed so that it will not saturate.
The effective transformer-choke volume is:
2max
2o(max)sr0
BIL
Volume =
0 = permeability of vacuum spacer = relative permeability of the chosen core material
Io(max) = maximum load currentL = output (secondary) inductance
Bmax = maximum flux density of the core
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Flyback Converters
, Sept. 2006. 808-PowerLab 21
41/57
Effect of the Leakage Inductance
Np : Ns+
+
oI
VoVin
Co RD
Q
LM
Transformer Model
Llk
Leakage Inductance
+ vlk
VinD1
n:1
TR1
Vo
Co
Vin
ton toff0
Primarycurrent
Seccurrent
Switchingvoltage
T
0
0
Ip
ISW
IS
ID
VceorVds
leakageinductance
spike
ISec =Idiode
Vin+Vo Vin
t
t
t
Ip = Vin.ton / Lp(discontinuous)
discontinuous
21
nn
Q(off)
p(max)lklk(max) T
ILv =
The induced leakage spike voltage is:
TQ(off) is the primary switch turn-off time.
42/57
Clamp Circuits for Flyback Transformer
DrainDrain
D
C R
D
Dz
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Flyback Converters
, Sept. 2006. 808-PowerLab 22
43/57
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Flyback Converters
, Sept. 2006. 808-PowerLab 23
45/57
Transient Oscillation Due to Mode Transition
(a)
(b)
(c)
(d)
CA E F
DB
KH
G J I L
N
M P S
RO
T X
YU
ZV
W
Tdt
Ip2Ip1Ip discontinuous
Ip2Ip1
Ip discontinuous
Ip continuous
Is continuous
46/57
C o m p o n e n t S e l e c t i o n : M a i n P o w e r M O S F E T
-
Flyback Converters
, Sept. 2006. 808-PowerLab 24
47/57
Design Considerations for Flyback Converters
Poor Dynamics: In flyback converters, the gapped transformer inductance results a zero in the right-half-plane (RHP), which makes the closed-loop compensation in CCM (continuous conduction mode) very difficult. Typically, the closed-loop bandwidth in CCM is very narrow and the transient response is slow. Larger Output Capacitor: In flyback converters, a large output capacitor is required due to the lack of a second-order low-pass inductor/capacitor filter at the output.
Difficulties in Flyback Transformer Design: Processing power is limited by the flyback transformer. It is hard to reduce the leakage inductance for when the processing power is increased.
High Blocking Voltage: Main power transistor blocking voltage must sustain 2Vin plus leakage voltage spike.
48/57
Multiple Outputs of Isolated Flyback Converter
An advantage of the flyback converter is it is easy to provide multiple outputs.
This is because the isolation element acts as a common choke to all outputs, thus only a diode and a capacitor are needed for an extra output voltage.
+
Vin
Vout,1
Vout,2
Q
-
Flyback Converters
, Sept. 2006. 808-PowerLab 25
49/57
Cross Regulation in Multiple Outputs Flyback Converters
The cross regulation of a multi-output flyback converter can be significantly improved by lowering the clamp voltage, especially to slightly above the reflected output voltage. However, it causes more loss in a traditional RC clamp. Some solutions for improving thecross regulation with low loss are provided and discussed in future publications. Larger leakage inductance in the secondary windings leads to better cross regulation of that output when it is lightly loaded.Larger leakage inductance in primary side will be beneficial to improve the cross regulation of multiple output flyback converters. However, it results more loss in a traditional RC clamp. Reducing core gap to achieve larger magnetizing inductance in flyback converter design will improve cross regulation.
50/57
Interleaved Flyback Converter
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Flyback Converters
, Sept. 2006. 808-PowerLab 26
51/57
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Flyback Converters
, Sept. 2006. 808-PowerLab 27
53/57
Control of a Flyback Converter
IsolatedFeedback
Vin
Vac
Vcc
Lp
Ls
Ip
IsVout
Drainn:1
Max. Duty cycle
Driv erOSCILLATOR Clock
Clock
COMP GND
S
R Q1
1/100
PWM OCP
LEB
Rsense
L6590L6590DL6590A
2.5V
VFB E/A+
+
0.5V
FrequencyCompensation
54/57
1.3 W, 24 Vin, 3.3 Vout Flyback DC-DC Converter
C1 C2
24V
GEN
R1
R2
C4
C5
CSC3
GND
16T 7TC9
C77T
C6
D1 D3
COMP
BYPASS
33F 0.1F
0.1F
0.1F
1F 1F
220F10MQ100N
10MQ100N
D2
3V3 400 mA
Feedback23TBAS21
180pF
27k
0.25
VNEG VOUT
VCC
LX
Si9121DY
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Flyback Converters
, Sept. 2006. 808-PowerLab 28
55/57
A 5W Flyback Converter with 170 Vin and Multiple Outputs
56/57
50 Watt, 48Vin, 5Vout, Isolated Flyback ConverterUsing a Primary Side PWM Control UCC3809 and the UC3965 Precision Reference and Error Amplifier
-
Flyback Converters
, Sept. 2006. 808-PowerLab 29
57/57
100VIN to 300VIN, 5VOUT at 1A Isolated Flyback Power Supply
Isolated Flyback Converter Regulates Without an Optocoupler
-
808 ()
-
Flyback Converters
808 ()
n : 1 +
+
IL
VoVin
Co R
Ying-Yu Tzou -
808 ()
Ying-Yu TzouFlyback Converter: Selected Reading [1] G. Chryssis, High-Frequency Switching Power Supplies: Theory and Design, Chap. 3: Types of Power Converters, McGraw-Hill Book Company, 1984.[2] Christophe Basso, Average simulations of FLYBACK converters with SPICE3, Technical Report, May 1996. [3] Sanjaya Maniktala, Chap. 6: Isolated topologies for off-line applications of Switching Power Supply Design & Optimization, 2004. [4] Bob Bell, On Semiconductor, "Two-switch topology benefits forward and flyback power converters," EDN pp. 107-111, September 1, 2000. [5] Design Guidelines for Off-line Flyback Converters Using Fairchild Power Switch (FPS), Application Note AN4137, Fairchild. [6] Ravindra Ambatipudi, Design of Isolated Converters Using Simple Switchers Using the LM2587, National Semiconductor. [7] MathCAD Design Example: Switching Power Supply Design: Discontinuous Flyback Converter, Michele Sclocchi, Application Engineer, National Semiconductor. [8] MathCAD Design Example: Switching Power Supply Design: Continuous Flyback Converter, Michele Sclocchi, Application Engineer, National Semiconductor. [9] Lisa Dinwoodie, Design Review: Isolated 50 Watt Flyback Converter Using the UCC3809 Primary Side Controller and the UC3965 Precision Reference and Error Amplifier, TI Application Note U-165, 1999. [10] Sanjaya Maniktala, Chap. 10: Flyback Transformer Design of Switching Power Supply Design & Optimization, 2004. [11] Technical Bulletin CG-03, For Flyback Transformers . . .Selecting a Distributed Air-Gap Powder Core, Magnetics. [12] S.-K. Chung, "Transient characteristics of high-voltage flyback transformer operating in discontinuous conduction mode," IEE Proc.-Electr. Power Appl., vol. 151, no. 5, pp. 628-634, Sept. 2004.slua086.Isolated 50 Watt Flyback Converter.pdfData SheetsUCC3809UC3965